ECE 415/515 –ANALOG INTEGRATED CIRCUIT DESIGN OPAMP DESIGN AND SIMULATION © Vishal Saxena OPAMP DESIGN PROJECT R2 vin/2 vout R1 CL vin vout VCM RL VCM CL (a) ECE415/EO VCM -vin/2 (b) R1 CL R2 ECE515 DESIGN SPECIFICATIONS TWO-STAGE OPAMP TWO-STAGE OPAMP: MILLER COMPENSATION MILLER COMPENSATION EQUATIONS TWO-STAGE OPAMP: ZERO-NULLING R VOLTAGE BUFFER COMPENSATION COMMON-GATE COMPENSATION CLASS-A STAGE: SLEWING CLASS-AB STAGE: FLOATING MIRROR TELESCOPIC+CLASS-AB STAGE Vbias2 Vbias5 • Note that in this schematic, Indirect compensation is used. • Cc is connected between vout and an internal lowimpedance node • For Miller compensation, connect Cc between nodes 1 and 2. • Vbias5 is generated using a replica bias circuit FOLDED-CASCODE STAGE FOLDED-CASCODE WITH CLASS-AB OUTPUT • Note that in this schematic, Indirect compensation is used. • Cc is connected between vout and an internal lowimpedance node • For Miller compensation, connect Cc between nodes 1 and 2. FC+CLASS-AB+RAIL-TO-RAIL INPUT GAIN ENHANCEMENT • Note that in this schematic, Indirect compensation is used. • Cc is connected between vout and an internal lowimpedance node • For Miller compensation, connect Cc between nodes 1 and 2. CADENCE SPECTRE STB ANALYSIS SPECTRE STB ANALYSIS • The STB analysis linearizes the circuit about the DC operating point and computes the loop-gain, gain and phase margins (if the sweep variable is frequency), for a feedback loop or a gain device [1]. • Refer to the Spectre Simulation Refrence [1] and [2] for details. EXAMPLE SINGLE-ENDED OPAMP SCHEMATIC STB ANALYSIS TEST BENCH • Pay attention to the iprobe component (from analogLib) • Acts as a short for DC, but breaks the loop in stb analysis • Place the probe at a point where it completely breaks (all) the loop(s). DC ANNOTATION • Annotating the node voltages and DC operating points of the devices helps debug the design • Check device gds to see if its in triode or saturation regions SIMULATION SETUP BODE PLOT SETUP • Results->Direct Plot-> Main Form OPEN-LOOP RESPONSE (BODE PLOTS) • • Here, fun=152.5 MHz, PM=41.8° Best to use the stb analysis with circuit is in the desired feedback configuration • Break the loop with realistic DC operation points SMALL STEP RESPONSE 10mV Observe the ringing (PM was 41°) ▪ Compensate more (↑ Cc and/or ↑ gm2) LARGE STEP RESPONSE 500mV Note the slewing in the output ▪ Class-A: I2/CL ▪ Class-AB: ISS/CC XF ANALYSIS (FOR CMRR, PSRR) • For CMRR and PSRR plots, you can use xf analysis. • Set up your testbench sources for the supplies (of course), but also a source representing the common mode voltage. • Then run an xf analysis and tell it where the output of the circuit. • You can then plot the transfer function from every source to the differential output of the circuit. http://www.designers-guide.org/books/dg-spice/ch3.pdf XF ANALYSIS • XF analysis simultaneously computes individual transfer functions from every independent source to a single output. TWO-STAGE OPAMP COMPENSATION TECHNIQUES MILLER COMPENSATION VDD Compensation capacitor (Cc) between the output of the gain stages causes pole-splitting and achieves dominant pole compensation. VDD VDD M3 M4 M7 1 220/2 750Ω vm M1 M2 vp iC ff M6TL M6BL iC fb CC 10pF 2 Vbias4 ▪ Due to feed-forward component of the compensation current (iC). 100/2 M8T The second pole is located at 100/2 M6BR Unlabeled NMOS are 10/2. Unlabeled PMOS are 22/2. CL 30pF Vbias3 M6TR An RHP zero exists at vout M8B The unity-gain frequency is x10 A benign undershoot in step-response due to the RHP zero ❖All the op-amps presented have been designed in AMI C5N 0.5μm CMOS process with scale=0.3 μm and Lmin=2. The op-amps drive a 30pF off-chip load offered by the test-setup. DRAWBACKS OF MILLER COMPENSATION VDD • The RHP zero decreases phase margin VDD VDD M3 M4 M7 1 ▪ Requires large CC for compensation (10pF here for a 30pF load!). 220/2 vm M1 M2 vp CC vout 2 10pF M6TL M6BL Vbias3 M6TR M8T M6BR M8B Vbias4 Unlabeled NMOS are 10/2. Unlabeled PMOS are 22/2. CL 30pF 100/2 100/2 x10 • Slow-speed for a given load, CL. • Poor PSRR ▪ Supply noise feeds to the output through CC. • Large layout size. INDIRECT (AHUJA) COMPENSATION VDD • The RHP zero can be eliminated by blocking the feed-forward compensation current component by using VDD VDD VDD M3 vm M4 M1 M9 1 ic M2 MCG vp M7 220/2 Cc 2 vout CL A 30pF M6TL M6BL Vbias3 M6TR M10T 100/2 M8T Vbias4 M6BR Unlabeled NMOS are 10/2. Unlabeled PMOS are 22/2. 100/2 M10B M8B x10 An indirect-compensated op-amp using a common-gate stage. ▪ A common gate stage, ▪ A voltage buffer, ▪ Common gate “embedded” in the cascode diffamp, or ▪ A current mirror buffer. • Now, the compensation current is fed-back from the output to node-1 indirectly through a low-Z node-A. • Since node-1 is not loaded by CC, this results in higher unity-gain frequency (fun). INDIRECT (CASCODE) COMPENSATION VDD VDD VDD M4T M3T M3B A Vbias2 ic M4B VDD VDD VDD M3 M4 M7 M7 1 220/2 110/2 Vbias5 1 M1T vm M1 M2 vp CC 1.5pF M6TL M6BL vout 2 CL vm A M1B M2B 30pF CC vp 1.5pF vout 2 CL ic 30pF Vbias3 M6TR M8T Vbias4 M6BR M8B 50/2 Vbias3 50/2 30/2 M8T M5T Vbias4 30/2 M5B Unlabeled NMOS are 10/2. Unlabeled PMOS are 44/2. M2T Indirect-compensation using cascoded current mirror load. Unlabeled NMOS are 10/2. Unlabeled PMOS are 22/2. M8B 100/2 100/2 Indirect-compensation using cascoded diff-pair. Employing the common gate device “embedded” in the cascode structure for indirect compensation avoids a separate buffer stage. ✓ ✓ Lower power consumption. Also voltage buffer reduces the swing which is avoided here. INDIRECT COMPENSATION: MODELING C c ic Rc A vin A1 A2 1 Differential Amplifier vout The compensation current (iC) is indirectly fed-back to node-1. 2 Gain Stage Block Diagram vout ic 1 sCc Rc 1 2 + gm1vs R1 + Cc C1 gm2v1 C2 R2 vout Rc - - Small signal analytical model RC is the resistance attached to node-A. Resistance roc is assumed to be large. The small-signal model for a common gate indirect compensated opamp topology is approximated to the simplified model seen in the last slide. gmc>>roc-1, RA-1, CC>>CA INDIRECT COMPENSATION: EQUATIONS j un p3 p2 z1 p1 • Pole p2 is much farther away from fun. • Can use smaller gm2=>less power! • LHP zero improves phase margin. • Much faster op-amp with lower power and smaller CC. • Better slew rate as CC is smaller. LHP zero EFFECT OF LHP ZERO ON SETTLING • Ringing in closed-loop step response • • Magnitude (dB) Causes gain flattening and degrades PM Hard to push out due to topology restrictions 40 20 0 -20 -40 180 135 90 45 Used to be a benign undershoot with the RHP zero, here it can be pesky Is this settling behavior acceptable? • Watch out for the ωz,LHP for clean settling behavior! • When using indirect compensation be aware of the LHP-zero induced transient settling issues 0 2 4 10 6 10 8 10 10 Frequency (Hz) Closed Loop Step Response 1 0.9 0.8 0.7 0.6 Amplitude • • 60 Phase (deg) • In certain cases with indirect compensation, the LHP-zero (ωz,LHP) shows up near fun. Bode Diagram 80 0.5 0.4 0.3 0.2 0.1 0 0 0.2 0.4 0.6 Time (sec) 0.8 1 1.2 -7 x 10 Small step-input settling in follower configuration REFERENCES 1. The Designer’s Guide to SPICE and Spectre: http://www.designersguide.org/books/dg-spice/ 2. Spectre User Simulation Guide, pages 160-165: http://www.designersguide.org/Forum/YaBB.pl?num=1170321868 3. M. Tian, V. Viswanathan, J. Hangtan, K. Kundert, “Striving for Small-Signal Stability: Loop-based and Device-based Algorithms for Stability Analysis of Linear Analog Circuits in the Frequency Domain,” Circuits and Devices, Jan 2001. http://www.kenkundert.com/docs/cd2001-01.pdf 4. https://secure.engr.oregonstate.edu/wiki/ams/index.php/Spectre/STB 5. Saxena V, Baker R.J., “Indirect feedback compensation of CMOS op-amps,” IEEE WMED 2006. REFERENCES 6. Saxena V, Baker R.J., “Indirect compensation techniques for three-stage CMOS op-amps,” IEEE MWSCAS 2009. 7. Saxena V., Baker R.J., “Indirect compensation techniques for three-stage fully-differential op-amps,” IEEE MWSCAS 2010. 8. Saxena V. “Indirect Feedback Compensation Technique for Multi-Stage Operational Amplifiers,” MS Thesis, Boise State University, 2007.
